Tuner for television receivers



Feb. 2, 1954 E. J. H. BUSSARD TUNER FOR TELEVISION RECEIVERS 3 Sheets-Sheet 1 INVENTOR.

[mmery J H fiussard "m 2). z wi ATTORNEYS Original Filed May 5, 1950 Feb. 2, 1954 E. J. H. BUSSARD TUNER FOR TELEVISION RECEIVERS Original Filed May 5, 1950 3 Sheets-Sheet 2 TS W g A Wu mv.

Original Filed May '5, 1950 Feb. 2, 1954 E. J. H. BUSSARD 2,668,198

TUNER FOR TELEVISION RECEIVERS 3 Sheets-Sheet 3 INVENTOR. [mmer J h. Bussard By @205, n. BOLJMOL ATTORNEYS Patented Feb. 2, 1954 TUNER FOR L'IIELEVISION'RECEIVERS- Emmery" J H. Bussard, Cincinnati, Ohio, assignor to Avco Manufacturing Corporation, .Cincinnati,.0hio, a corporation of'Delaware Original application May 5, '1950, Serial No.

160,316, new Patent No. 2,615,983, datedOcto- 7 her 28,1952. -Divided and this application May 8, 1951, Serial No. 225,083

'2 Claims. (Cl. 179-171) The present invention is adivision of my United States Letters Patent 2,615,983, issued October'28, 1952. I The present. invention embraces an improved tuner which is of particular utility as embodied in a television receiver. The tuner is, in customary parlance, referred to as the front end of a tele vision receiver and the primary objectives of this invention are to providea particularly unique front end circuit having satisfactory gain and signal-to-noise characteristics and adequateperformance in. other respects. The tuner provided in accordance with theinvention is of the continuous type-ethat. is, it. is continuously. tunable by one manual operation through the lower standard television broadcast band beginning at 54 megacycles through all bands including the upper television broadcast band ending at 216 megacycles. 'The primaryobjectof the present invention is to. provide a tuner which satisfies the following requirements and aims:

(1)" The provision of a workable match between the radio frequency (R. F.) stage tube input .impedance and the antenna transmissionlineimpedance throughout thev television broadcast range;

.(2) -To maintain this desirable match, to minimize the spurious responses which tend to be introduced by. interfering signals such as. thoseflof intermediate frequency and image frequencies, and to attenuate all frequencies below those of the order of 34 megacycles;

(3) To enhance selectivity by tuning both input and output of the radio frequency amplifier stage;

'(4) To minimize radiationof local oscillations;

(5) To provide an economical tuner construction of enhanced gain and signal-to-noiseratio.

Anotherobject of the invention is to. provide a tuner construction which incorporates adequate shielding and at the same time minimizes stray currents and inductances. Another fundamental object of the present invention is to providea novel structure and method of construction whereby the undesirable effects of the inductances of leads and connections at very high frequencies are "minimized.

'For'a better understanding of the present invention, together with other and further objects, advantages and capabilities thereof, reference is made to the following description of the'accompanying drawings, inwhich there is showna preferred illustrative tuner in accordance with the invention.

In: the drawings:

.Fig. 1 is a; circuit schematic. of my improved tuner;

Fig. 2 is a front perspective view of a tuner assembly including the circuitry, provided in accordance with one invention;

Fig. 3 is a rear view of the main vertical .divider member of the assembly showing tubes mounted in place;

Fig. 4 is a fragmentary rear view of the mechanical assembly showing only theso'cket and mounting for the radio. frequency amplifier tube, before soldering in place;

Fig. 5 is a rear View of the main vertical-divider as it appears before th placement of components thereon; and

Fig. 6 is a sectional view taken. on line. 6.6 of Fig. 5.

Referring. now specific'allyto'v Figs. 1, and,2, it

will be observed that the major tuner components are a radio frequency amplifier tube'lll, aMmiXer or frequency-changing. tube H, .allocal oscillator tube 12, (elements H, 12 being in,..the same. envelope), and a three-circuit ganged inductor comprising variable inductances l3, land 15 (shown in Fig. 1 only), the inductorsbeing ganged, for unicontrol by any suitable mechanical expedients indicated by the dashed. lines I6, I! and 18. l The preselector or R. F. amplifierstage has. a novel tuned antenna input circuit provided-inaccordance with the invention. In the :specific example shown, this circuit iscoupled toan-unbalanced line-such as a ohm twin lead cable i9, 20. This lineworks into and is coupled to :a three-element reactive network 2|, 22, 23 for matching the impedance ofthe line-to th input impedance of the tuning circuit [3, 28,129. -.This network is of the 1r-type and it comprises a shunt inductor arm 2|, connected to the transmission line input leads and between terminals 26,. 21,;a series capacitor arm 22 connected between terminals 26, 24, and a shunt-capacitor arm 23'connectedbetween terminals 24,25. This network transforms the resistance load which is offered at the terminals 24, 25 looking toward tube 10, to the value of resistance, at terminals 26, 21,;required to provide a characteristic impedanceload for the transmission line I9, 20. Theoptimum match occurs at approximatelythev geometric mean (108 megacycles) vof therangeextending from 54 to 216 megacycles.

In this manner, whenthe tuner issetafor 108 megacycles, an impedance of approximatelyflo ohms, looking into terminals' '24, 25. across-which capacitor 23 is connected; is transformed into an impedance approximating .150 ohms, looking into terminals 26, 21 (in the direction of -tube I0). This network. provides a workable match throughout the range of .received signa ls, the

match varying within tolerable limits with the tuning. Capacitors 22 and 23 are in effect a capacity divider which steps the impedance down to approximately '70 ohms at terminals 24, 25, when the receiver is tuned to 108 megacycles.

Inductor 2| performs several useful functions in addition to its service as a parameter in the impedance transforming network 2|, 22, 23. It functions as a high pass filter efiectively shorting amplitude modulation (AM) broadcast signals to ground, such signals being those broadcast in the 540-1600 kilocycle band. The inductor 2| also serves as a direct current leakage path, and it prevents the undesired accumulation of static charges on the antenna.

The dimensions of inductor 2| and capacitor 22 are such that these two elements are series resonant at a value between the selected intermediate frequencies and the R. F. carrier frequency of the lowest channel. In the particular illustrative embodiment shown, these two elements are series resonant at approximately 34 megacycles. At 34 megacycles, then, there would effectively be a short circuit between terminals 24 and 21, and terminals 21 and 25 are placed so closely together that there would be in effect a short circuit between terminals 24 and 25, so that the input circuit of the radio frequency tube l0 would receive substantially no signal voltage at the frequency of 34 megacycles or at frequencies near that value, such as the intermediate frequencies. The values of inductance 2| and capacitor 22 are so chosen as to provide further good intermediate frequency signal rejection.

In determining the values of capacitor 22 and inductor 2 I I have endeavored so to choose them as to produce an effective short circuit between terminals 24 and 21 at some predetermined frequency. In pursuance of an established design principle, I have approximated that frequency at 150% of the mean of the sound and video intermediate frequencies. Then I have made some comprises in favor of the use of commercially available components and in one successful embodiment of the invention so shaped the elements 2|, 22 as to make them resonant at 34 megacycles. Since at that frequency the elements 2 I, 22 in effect create a short circuit across terminals 24, 25, it will be seen that undesired signals of that frequency are highly attenuated. Now, then, as undesired signals of progressively lower frequencies are considered, capacitor 22 presents a progressively effective series impedance to them and inductor 2| presents a progressively effective shunting impedance so that at the broadcast range of 540 to 1600 kilocycles, the inductor 2| simply short circuits the undesired signals to ground. Throughout the frequency range from direct current up to 34 megacycles, the elements 2|, 22 function as a good high pass filter.

In the illustrative embodiment shown, the parameters of inductor 2|, capacitor 22 and capacitor 23 are so chosen as to be parallel resonant at a value, for example, 47 megacycles, below the R. F. carrier frequency of the lowest television broadcast channel, 54 megacycles, so that the parallel resonant circuit 2 Ii, 22, 23 looks like a capacitance to the tuned circuit 13, 28, 29 throughout the range of operating frequencies.

A primary aim in the tuned circuit comprising inductors |3 and 28 and capacitor 29 is to build up a large B. F. current flow through capacitor 29. Another primary consideration is to make the tuning of this circuit substantially dependent on the manual variation of inductor l3 only and as independent as practicable of capacitance parameters. It will be appreciated that capacitor 29 is preset at the factory. It should be borne in mind that there is a return path for current flow in the selector circuit comprising the elements I3, 28 and 29, this return path existing between terminals 24 and 25 and comprising a number of branches, one of which consists of capacitor 23, another of which consists of the series combination of resistor 82 and capacitor 8|, the third of which comprises the series combination of capacitor 22 and inductor 2|, the inductor being paralleled by the antenna system. It is essential that this multi-branch return path between terminals 24 and 25 be capacitive throughout the tuning range, so that it will not introduce an inductance parameter into the tuned selector circuit. It is also essential that the capacitive reactance of this return path be low with respect to the capacitive reactance existing at the input of tube I0 and between terminals 9 and 3|. The ratio of these reactances should be on the order of 2 to 1 as a minimum.

While resonant circuit 2|, 22, 23 is made to look like a capacitance existing between terminals 24 and 25, so far as the tuned circuit I3, 28, 29 is concerned, it is also desirable to build up a high current through capacitor 23 and therefore the circuit 2|, 22, 23 is made resonant at a frequency as close as practicable to the lowest operating frequency of 54 megacycles. In one successful embodiment of the invention, I have chosen a value of 47 megacycles as the resonant frequency of the circuit 2|, 22, 23. It will be appreciated that if this circuit did not look like" a capacitance to the selector circuit [3, 28, 29, it would introduce an undesired inductance parameter into the latter circuit which would limit the operating range and impair tracking among the two selector networks at input and output of the tube l0 and the oscillator tank circuits.

This tuner provides a gain, on the order of 6 db between the antenna terminals and the input terminals 9, 3| (Fig. 1), a particularly significant feature when it is considered that many commercially available tuners for television receivers show a loss between the corresponding points.

The input impedance of tube if! considered alone, a type 6036 being chosen for this illustrative embodiment, varies from approximately 9,000 ohms, at the low or Channel 1 end of the R. F. range, down to 500 ohms at the high or Channel 13 end of the R. F. range, while the impedance looking toward the tube into terminals 24, 25 approximates ohms at the mean of the range of R. F. frequencies.

While the effective impedance of tube Hi, considered alone, varies between the wide limits mentioned, the input impedance between the control electrode of tube l0 and terminal 34 is maintained within relatively narrow limits on the order of 1500 ohms. In one successful embodiment of the invention, the variation was found to be between the limits of 1400 to 1650 ohms across the whole tuning range. This result is achieved by reason of a network 32, 33 which is provided between terminal 34 and the cathode of tube ill, as will be explained hereinafter. The circuitry provided in accordance with the present invention between terminals 24, 25 and the input of tube I0 is highly selective and at the same time provides adequate impedance transformation from 70 ohms to the input circuit impedance of tube III. For these purposes I provide an L network composed of reactive elements as follows: A series combination of variable inductor i [3; end-.5 inductor: 2 8i and'itrimmerrcapacitorr2932 effectively 'connected-rinzseriesiacross terminals 2 4; 25;. Themapacitiveaelement:29'3is connectedfibe tween one lead bfiboil 28-and terminal 3|;terminal.3l. being so-closerto terminal 25iasrto be 'effectively at the same potentialgand that lead'of coil. l28'salso being connected to: the control elec= trcde of tube llil The'elements l3, 28; and- 29 comprise a: series:selector circuit which is: manu-' ally varied to be resonant at the desired ch'anneI' IO and to :tune theinput -oftube 0. This being a'. seriesresonant I circuit; it aifords the selectivity characteristicaof- -such circuits an'd at the same time provides a very-sub'stantial"gainrapproxi- 1 mating the product of. theselector circuit Q"- and l5- theinput voltage across terminalstflfi 253 It willbe -observed: that f the -Series "resonant Lcircuit l 3 28; 29 has a ldw impedance input-approximating v 70 ohms -and a high' impedance output (across capacitor 2 9 7: on the order ofithe tube input impedancebetweem terminals 9, 3 I;

Referring now--- specifically 'to 1 the 1 radio frequency. amplifying tube .1 fl a pentode is employedandits cathode isconnected to grounded -point 34 through-a biasingresistor 32-." The inputcir=- cuit' 'of--tube I0 is *so shaped as to' accomplish the-following objectives (1) To minimize varia-- tions ininput capacitance withtransconductance, so that, looking into the-tube atterminals 9, 3 I-, there is presented a relatively-stable input capacitance-thus precluding the introduction into theselector network ofa wi'dely= varying frequency determiningcapacitance parameter and again assuring: that trie selectr ir network tuning I is accomplished substantially-by the-variation of 35' inductor :l 3'only;"(2) To present a relativelycon stant -hig'h resistive-"load"across terminals 9, 3|, this load-being suficiently: large-tomaintain an adequateres-ponse throughout the high frequency a range underconsideration.

Aacath'ode I resistor "32 3 is :provided in: part for the. purpose of stabilizing the 1 input capacitance of. tube 1 0; and thisresistor is connected between the' zcathode terminal andz point 34; A- -value-of" 120:'ohm's.-

suitable for :this resistor, although I do not desire todoe limitedtothis s zieciflfrillus trative'- value: As indicatediat pages-=15 and 16'" of: RCA Application Note :AN-118;--published April 15,2..1947," by the Tube Department' Radio -Cor-- poration .of America;-' Harrison; New Jersey; the undesired change; in: input capacitance Wi171ftransconductance is reduced bythe-use-of an=- unbypassed cathode-resistor; such: aszel'ement 32; in series: with" thie -cathodes In the absence -of thisresistorzthe pentode input-capacitance would tend toz vary -with' .gri'd bias:- Thisefiect; known i as:the:Miller efiectg is *ofimportanceibecause ifi wouldz'tend :to :detune the-:selector icircuit l3,= 28; 295.. Miller efiectiisminimized by incorporating-- a small amount of degenerative feedback, the sor lattembeing: most easily accomplished by leaving the .cathode resistance unbiased for The value .of.=thearesistor required -depen'ds -=upon--the change of transconductance from cut-ofi to= 'oper atinggconditions, the grim-cathode transc0nduct ance of theatubefand the coldgridto-cathodecapacitance: To obtain full compensationforcapacitance change, it canbe demonstrated that it. is necessary tonmake r the product of cathode' resistance: and: gri'dcathode transconductance equalito :the ratio of ltheincrease :in: capacitance tothe-gridecathode eapacitancei Theu-nbypassedcathode :resistom reduces athe effective: transcon 1 ductanceiand gain by an 'amount which' increases witmtheivahiezofetheicathode--resistom Ai"a*-arti 6. fici'aiuincreaseeimthe :amount iof ztheccoldzlgridsto cathbde .capacitance permitsx: the-c use of smaller resistor value and-lessens the IOSSIOfEEIim... leading to improved overall: results; This. purpose: can-be accomplished. by connecting a small capacitor between the :grid 'andicathode; Inlrace cordance withf-the invention; the last-mentioned" capacitanceparameter isi'supplie'd by twocapaci-i. a tors-in series; 33?v and 2 9,5 the 'series "combination;

bein'g located in circuit betweenthe control 'elec-a. trade-"and the cathode .and. thereforeiin:parallelzt with the grid-cathode interelectrode capacitance;- The use' of too large a. value of ecapacitance :for: this-purpose .would have an.- unfavorable: effect pm the input. conductance of. the tube;

Anothereiiect :of :the use. .of l the degenerative: resistor- 32, supplying. current :feedback,: tosina crease the input impedance offered by then-tube totheapplied signalvoltage as seen lookingiintori' the terminals 9," 3 l, and-Ito assist inamaintaining c that-tube simpedancesufiiciently hightto prevent:-.. undue damping of the tuned circuit.

It is not possible to divorce the discussionzof the arrangements' made to stabilize inputicapac-z itance and those made to stabilize inputa 'cons ductance, the two being so intimately related; At high frequencies the tube input conductance componentsdue to transit time effects; tubelead'l inductanceand feedback through thegrid=plate capacitancefrom the plate circuit are effectively in parallel with the tuned grid'circuit. The coni-i.- ductance' components due-to'transit time ieifects and tube lead inductances are positive in. signand vary with the square-of the frequency.- The. input conductance: component due to feedback through the grid-plate capacitance, measuredat the grid circuit resonant frequency, is negative in the particular illustrative embodiment shown; the plate load of tube. H3 being so dimensioned as I "to incorporate'an inductive component, the lead I inductance between the anode of tube 10 and the inductor 39 andother distributed inductances being adequateto make the plate load as a whole appear to have an-inductivecomponent. In theabsence of special precautions, the. input conductanceof a pentodetends to vary rapidly over the television bands.

It having been indicated that it-is not possibletosegregate completelyfor purposes of discussion otheeffects of varying input capacitanceandim put-conductance, and it having been pointed outhowthe feedback network 32, Hand 29-is effective to stabilize input capacitance, the same net-' work is likewise effective to stabilize *input'con- .ductance-and tomaintain it low-throughout the-- desired range. I

One objectiveof my-feedbac-k network-isto prevent incorporation in the selector network of-=-' excessive shunt "capacitance, and therefore' I ;;maketheseries -capacitor 29 sufli'ciently small to satisfy this requirement. At-thesame time it is desired to incorporate a frequency sensitive network such'th'at the degree component of fedback-voltage 'will not remain in phase at fre--- :quencieswh'ere oscillations might occur due-toincreased input conductance,- such conditions normally occurring and appearing aspara'sitic oscillations; Therefore I incorporate in the feedback networkand in series-with the small capac= ;itor "29"another"capacitor 33'which is large-invalueby comparisonwith'the valuea neutralizingcapacitorwould haveif itwere directly connected between point 6 and: terminal 30? Atthe 'sarn'e time: as indicated ab'ove;* the capacitor "'3 3 has ireaetan'ce large bycomparison withits shunting cathode resistor at normal operating frequencies, whereby resistor 32 is not B. F. bypassed at operating frequencies.

A substantial economy is accomplished by making the cathode resistor 32 sufficiently large to function as a biasing resistor, thus permitting the omission of a bypassed resistor in series with it. It is recognized that, when resistor 32 is made sufiiciently large to perform this additional function, it introduces more degenerative feedback than is optimum for purposes of stabilizing input conductance and capacitance. However, since the effect of an inductive plate load and the gridplate feedback is such as to introduce re eneration, the plate circuit is so shaped as to compensate for the additional degeneration introduced when. resistor 32 is made sumciently large to function as the sole cathode resistor. Additional compensation is obtained by increasing the effective amount of cathode lead inductance by deliberately spacing point B from the socket cathode terminal.

The screen grid is connected to the positive terminal 35 of a suitable source of space current indicated by the symbol +B through a screen dropping resistor 35, bypassed by a capacitor 37, and a resistor 38 in series with resistor 35. The suppressor electrode is grounded. The anode circuit is connected to terminal 35 through a series combination of inductor 39, variable inductor I4 and resistor 38, terminal 40 of variable inductor I4 being connected to th junction 4| of resistors 36 and 38. A damping resistor 42 is connected in shunt with the series combination of inductor I4 and resistor 33, more damping action being desired at the low frequency end of the operating range. The selector circuit intercoupling amplifier tube In and mixer tube II is tuned to the desired operating frequency by adjustment of inductor I4, that inductor being a part of a parallel resonant circuit comprising an inductance branch consisting of inductors 39 and I4 and a capacitance branch consisting of adjustable capacitor 43- and capacitor 44. Junction :5 of these two capacitors is connected to ground at 46 as shown. This tuned selector network 35, It, 43, 44 in the anode circuit of tube In is coupled to the control electrode input circuit of a triode mixer tube II by a conventional network comprising coupling capacitor 4'I and grid resistor 48, the latter being connected between the control electrode terminal 49 of mixer tube II and ground 50 (Fig. 1).

Local oscillations are supplied to the control electrode input circuit of the frequency changing tube II by an oscillator including tub I2 and associated circuitry. This oscillator is described in detail in my Patent No. 2,579,789, issued December 25, 1951, entitled Tuner for Television Receiver. Reference is made to that patent for a detailed description of the oscillator. Briefly, however, this oscillator has a grid tank circuit comprising an inductor 52, an inductor 53A, and the distributed inductance of conductor 54, the terminus of the latter being R. F. grounded and effectively connected to the cathode of tube I2 by a capacitor 55. The capacitance of 55 is so large that it is not a substantial frequency-determining parameter in this tank circuit. The inductance branch comprising elements 52, 53A, and 54 is paralleled by an adjustable capacitor 56, R. F. connected between cathode and control electrode of oscillator triode I2.

The oscillator also has a plate tank circuit comprising inductor 53B and the distributedinductance of conductor 54, the inductance branch 53B, 54 being paralleled by a capacitor 51, connected between anode and cathode of tube I2.

This oscillator is provided with the usual grid capacitor 58 and grid resistor 59, the latter being connected between the control electrode of tube I2 and the grounded point Bil. Local oscillations are injected from the grid tank circuit of this oscillator into the control electrode circuit of the mixer triode I I by a coupling network comprising a series combination of a capacitor SI and an inductor 52, this series circuit being tuned to a resonant frequency considerably above the range of operating frequencies, for example 340 megacycles. The frequency range of the local oscillations may extend from 80 to 240 megacycles, for example, while the range of received signal frequencies extends from 54 to 216 megaoycles. I do not desire to be limited to any specific selection of frequencies, and have mentionedcertain frequencies and dimensions herein for v purposes of illustration only and not of limitation. The advantage of the coupling network BI, 52 is that the coupling between the oscillator and the frequency-changing tube I I tends to become more resistive and less reactive as the receiver is attuned to higher operating frequencies, thereby compensating for the natural tendency of the output of the oscillator to decrease in intensity.

The distributed inductance of conductor 54 is common to both plate and grid tank circuits, so that a portion of the voltage fed back from the plate circuit to the grid circuit is applied to the grid circuit through this common inductance. The capacitors 55 and 51 function as a voltage divider network between input and output circuits, the voltages for their respective terminals remote from one another being approximately degrees out of phase, so that feedback also results from this voltage division. This oscillator possesses a high degree of stability throughout its range of operation, for the reason among others that both oscillator tank circuits are tuned in unison. Tuning is accomplished by adjustment of variable inductor I5, the latter being connected across inductors 53A and 533. A common coil having a tap 63provides inductor portions 53A and 53B. The D. C; path for anode voltage may be traced from terminal 35 through conductor 54 and inductor 533 to the anode of tube I2. Inductor 52 is magnetically isolated from inductor 53A, and there is essentially no magnetic coupling therebetween.

Each of the grid and plate tank circuits, con: sidered alone, is tuned below the operating frequency so as to appear capacitive at each operating frequency. As stated, the oscillator is adjusted as to frequency by manual adjustment of inductor I5, it being ganged with inductors I3 and I 4.

It will be understood that the tuning elements comprising inductors I3, I4, and I5 and their ade 1 Justable contacts 65, 66, and I, respectively, are

included in a three-gang spiral continuously variable ganged inductor which may be of the gen'-. eral type shown in Fig. 167, page 151, of the Photofact Television Course, March 1949, How- 65 made of high silver content alloy or the like, possessing spring properties, rides on an inductor,

such. as that indicated by; the: reference numeral I3;.made:-.-of-silver wire or ribbon. Theslid-ing .contacton-shorts the unused.- portion of the inductance; Sincegangedinductorsare per se well known, theelements I3,- I4, I5, 65, 66, and i need not be shown in. detail herein .and are omitted from -Fig.- 2.

The mixertube II'and oscillator tube I2may be comprised. of different. sections of a type 12AT7 tube, for'example. It will, of course, be understood that separate tubes in separate-envelopes may alternatively be used. The mixer tube has aplate load. consisting of a series co1nbination of .induotor I0, iron core adjustable inductor 'II, andinductor12, the-anode circuit being completed-for high frequency signals by a capacitor 55: Between grounded point :13 (Fig. 1) and the junction .of inductors"); .Il isconnected aacapacitor 14.

As indicated .in RCA Application Note AN-l38, published M6.-lTCh-':15, 1949, by the .Tube Department; Radio Corporation ;of America, Harrison, New-Jersey, it isimportantthat the plate circuit beinductive to the tuned R. F. frequencies. The mixencircuitincluding tube I I is so arranged as toprevent two. undesired contingencies: (l) oscillation at R.-:F; .or-I.1F.; (2) undesired dampingrof theinput-circuit :atlR. F. To this end capacito-r- I4-- is connected between the junction of coils;- 10,. 'II and ground,.,inductor I and capacitor:v 74 together forming a. series resonant circuitwhichresonates slightly above the maximnm. operating; frequency (216" megacycles). This: circuit I4 lookslike a. very low impedanceat resonance .to .R; F. and-therefore unloads. the. platecircuitat R. andprevents a high impedance. from being built up; across the plate circuitatR. .E., therebyrten'ding to preventaoscillati'ons. On the otherhand,inductance 'Iilcis too-small to. present. any substantial .impedance: to I. F., .and the-capacitor. I4: is tuned outzforl. F.

The plate.load-:of itube II appears inductive to the input circuit'ofthe tube at.R., F., thereby introducing. a. negative;resistance factor into 1 the grid circuit, which compensates for the damping factor of'the normal :tube loading and therefore in effect increases the Q of the grid input. This input be ng tuned .-to R: a high impedance is accordingly effected .for R. F., while :a relatively low impedance; is :presentedto I.LF..' as'fed back through the grid-plate capacitance.

Ithasbeen indicated that for -I. a high impedance exists between terminals I3 and '5. This impedance is-transformed intoa relatively low impedance output by the L,-type. network:com prising-windings] I and .12, the output impedance being: on the order of 350:0hms.

One filament lead of tube. [0. is connected to ground; and another/to the ungrounded filament supply :terminal 16,. either direct .or alternating current being suitable for this supply, heaterbypass-capacitor TI being provided for the heater of tub'e III.- The filament connections for'the tubes I I and I2 are similar tothat for tube I0, but no additional bypass capacitors are employed.

Automatic gain control potential is supplied to the grid of tube IOfrom terminal 80; the-latter being connected to -an appropriate source of automatic-gain control potential (not shown). This source may beidentical to that-shown in U." S. PatentNc; 2,559,038 to-Bass, issued July 3, 1951.

Interposed between the AGUsource-and the control electrode-is a=fllter network comprising-a shunt capacitor-BI :and a series resistor 82, the latter being in. series with inductors i3 and 28 and the grid of tube I 0. Since the combination of resistor 82 and. capacitor 8| is inshunt with capacitor-23,- it resistance loads the signal input circuit between terminals 24 and 25 and provides additional damping.

Beforev discussing the mechanical assembly providedin-paccordance with the present invention, certain'advantages of the circuit hereinabove describedare pointed-out. Oscillator radiation is particularly'low-with: this tuner, because thecornbinationzof 'inductorsal3 and 28 presents avery high series-3 impedance to oscillator frequencies, while-capacitorr23affords a, very low shunting impedancerto "those-frequencies, so thatthey are highly: attenuated.

onei-ofzthe'. primary advantages of this tuner circuit :isthat the selector network I3, 28,v 29 pro.- duces acvery substantial gain between antenna and R. F. stage-input when. tuned to resonance, provides-:goodiselectivity and rejection of undesired: signals; and enhances the signal-to-noise ratio.

Since both :input 1 and output circuits of the radio frequency; amplifier stage I 0 are tuned to the :desired channeL. the selectivity characteristics of this tuner: are very desirable. The gain characteristics are enhanced. by .the effective voltage amplification" occurring in the first selector network I3, 28;.29',.and bythe second selector network 39, I4,.44; I". The pass band characteristics1of;both selector networksare adequatev to assure satisfactory-fidelity. Inductor 2| bypasses signals of. intermediate frequency to: ground. Heterodyne detection of two signals having a frequency difference. lying. within ..the tuning :rang-e of the receiver, and. resultant cross talk. are suppressed'zby-stheztuned input circuit I3, 28,.29I'between the grid of theR. F. tube I0 and the antenna; that .zcircuit :preventingthe .undesiredrone of the interferingsignals from reaching the grid oftubesIll.

Image response is reduced because the two selectorrnetworks. suppressimage. frequency signals before application to the input of the mixer tube-II. Shielding preventscoupling ofundesired strays, including intermediate frequency harmonicsproduced by the second detector, into the radio frequency input circuits. It will be observed that the shunt input capacitance of tube I 0;- parallel withcapacitor 29, is one of the frequency determining parameters of the tunable selector network comprising elements I3,- 28, and 29. Further, the-outputcapacitance-of tube I6 and the input capacitance of tube I I are-eifectiv ly in shunt with capacitor 43 and are frequency determining parameters in the tunable selector circuit includingtheelements 39, I4; 43 and A l.

While-I do not desire to be limited to any specific circuit parameters, the latter varying widelyinaccordance with specific-design requirements, the following have-been found to be entirely satisfactory inone successful embodiment of the present invention:

Transmission line I 9, ohm twin lead; 20.

Resistor- 82; ohms. Resistor 32; IZO-ohms; Resistor 36 15,000 ohms.

Resistor-42: 5600 ohmsc l1 Resistor 38 68 ohms. Resistor 48 1 megohm.

Resistor 59 15,000 ohms.- Capacitor 22 27 micromicrofarads. Capacitor 23 27 micromicrofarads. Capacitor 8| 1500 micromicrofarads. Capacitor 29 0.8 to 6.5 micromicro- 'farads, adjustable.

Capacitor 33 3.3 micromicrofarads. Capacitor 31 1500 micromicrofarads. Capacitor 11 1500 micromicrofarad-s. Capacitor 44 1500 micromicrofarads. Capacitor 43 0.8 to 6.5 micromicrofarads, adjustable. Capacitor 41 6 micromicrofarads. Capacitor 14 15 micromicrofarads. Capacitor 55 1500 micromicrofarads. Capacitor 6| 1 micromiorofarad. Capacitor 56 0.8 to 6.5 micromicrofarads, adjustable. Capacitor 58 6 micromicrofarads. Capacitor 51 6 micromicrofarads.

Distributed inductance .01 microhenry, approxiof conductor 54. mately. Inductor 2| .82 microhenry, approximately. Inductor I3 .025 to .715 microhenry,

approximately. Inductor 28 .03 microhenry, approximately. Inductor 39 .02 microhenry, approximately. Inductor I4 .025 to .715 microhenry,

approximately. Inductor I .03 microhenry, approximately. Inductor 1| 2.3 microhenries, ap-

proximately. Inductor 12 .28 microhenry, approximately. Inductor 53A .25 microhenry, approximately. Inductor 53B .27 microhenry, approximately. Inductor 52 .035 microhenry, ap-

proximately. Inductor I5 .025 to .715 microhenry,

approximately. Inductor 62 .2 microhenry, approximately.

The characteristics of a type 6036 tube are fully described and tabulated in Application Note .AN-143, published March 31, 1950, by the Tube Department, Radio Corporation of 'America,

Harrison, New Jersey.

The description now proceeds to the'mechanical assembly in accordance with the present invention. It will be understood that the elements 90, 9| in Fig. 2 are the terminals of the oscillator tuning inductor I5. The two elements numbered 92 and 40, H are the terminals for the variable inductor I4 which tunes the output circuit of the radio frequency stage. The elements numbered 30 and 24 are the terminals of variable inductor I3 which tunes the input circuit of the radio frequency amplifier stage. The ganged inductor comprising the windings I3, I4, and I5 is not shown in Fig. 2, and. reference is made to my above-mentioned Patent No. 2,579,789 for a detailed showing as to the method by which the subassembly illustrated in Fig. 2 is mounted on a rectangular can containing the ganged inductor elements.

The subassembly illustrated in Fig. 2 i pported on a horizontally extending metallic base member 93, suitably cut out to receive contacts 90, 9I 92, 40, 30 and 24, and provided with integral mounting feet 95, 96 and a vertically extending metallic divider member 91, formed integral with base plate 93. Another vertically extending metallic divider member extends transversely of the members 93 and 91 and shields the components between the transmission line and the input circuit of the radio frequency amplifier stage I0, as well as the input circuit components of that stage, from the other tuner components. It will be understood that points such as 3I and 25 illustrated in Fig. 2 represent the termini of leads which are soldered to the vertical divider 91, the latter providing a common ground. In one practical tuner the length of the divider member 91 is approximately 4 6 inches. The base 99 for the radio frequency amplifier tube l0 (Fig. 2) and the base I00 for the oscillator and mixer tube sections I2 and I I are located very close to the ganged inductor portions with which they cooperate, base 99 being disposed above and between contacts 92 and30. Tube base I00 is located above and near to contacts 90 and 92. The dashed lines, such as that numbered C43, designate circuit components, such as the capacitor 43 symbolically shown in Fig. 1, which are simply suspended by their soldered leads in accordance with conventional practices. As a further example, the element numbered R48 in Fig. 2 designates the grid resistor 43 of the mixer triode II. Those components which are shown in detail in Fig. 2, such as inductor 39, inductor 52, inductor 62, inductors 53A, 53B, inductor 10, inductor 12, inductor 28, inductor 2|, and iron core inductor II, have the same reference numerals as in Fig. 1. The unit illustrated in Fig. 2 has input line I9 and 29 from the antenna, an automatic gain control lead ter minating at 89, an ungrounded heater supply lead passing through point 16 and terminating at the filament of tube III, a high voltage supply lead terminating at point 35, and an output lead terminating at the junction of coils H, 12. It will be observed that all grounded points in the radio frequency stage, shown in Fig. 2 to the right of divider 98, are very close together. Further, all grounded points shown to the left of the divider 98 are rather close together, the vertical divider 91 being very small. The layout is therefore such that lead length and stray lead inductanoes are minimized.

Referring now to Figs. 3 and 4, it will be observed that the envelopes of the two tubes I0 and II, I2 project rearwardly from the divider 91, the divider being suitably apertured to receive the tube bases I00 and 99. The base 99, for example, as seen in Figs. 4 and 5, is secured to a metallic member I02, which is provided with a plurality of upstanding spring arms for grasping the shielding can IOI in which the tube I0 is contained. The divider member 91 is formed with integral projections I03, I04. The projections I03, I04 fit into apertures in member I02 to position it. Solder is applied at points I03, I04 to secure member I02 to divider 91. The mounting of the tube base I00 is similar but need not be shown in detail herein. Referring now to Figs. 5 and 6, there is shown another important novel feature provided in accordance with the present invention. It will be observed that'the divider member 91 is formed with integral tangs I00 and I01, which are soldered, respectively, to the filament terminal I09 and the suppressor electrode terminal I I9 of tube.

zmccsyics RebasezS 9: for tube: I0. ,-Additionally,ithe; divider- 91 cisaformedavitir .integralctangs i Ii, 2 I2, II 3, I I4, --whichaares soldered; respectively, .toithe:contacts I15 '2 .(cathode) II 5 (heater), I'll v.(heater) and H81 (cathode): ofathe .base ifiilfforitube II; i2' .(see -F!ig:;2). it. willzzbe understood: that theibasez-Ilill asisupplied by. .themanufacturer has integral terminals I 15,. H 8,; I 11,. and: I ll? 'whichcproj ectzoutrivardly and at rightanglesto' the'main insulating .member onbase I00. inaccordancewith the inventicn, I'preformthe divider .inember: 9 I: with the "integralztangs .above describedend simply push the :base. members-1:99 .and' mi] intdplace. When 'they:'.are incplace I: bend the-terminals II5, I It,

proximatelysQO:degrees, and-'s'olderthem to their respective tangs already preformed on divider. 9]

This process .01":manufacturesrapidly and1eco- 01101131109111}; :eassures :minimum socket zbase .lead

lengithseand 1 alsov minimizes .the; .introductioncof i "an; inputrtuner' for; artelevision receiver; a three element type: reactive :network; having: two: arms for matching the impedance of an unbalanced transmission line (i9; 29).=-t0. the input impedance of a selector circuit (I3, 23, 29) comprising: an

input shunt inductor'arm (2 I connected across:

said transmissionline; a series-z-capacitor (22) connected between the high. potential terminals .426, 24.) of the arms, and an output shunt capaci- Ltor arm '(23)"said'in'ductor arm providingrat- Ltenuationnof carrier'signals halving frequencies;

.,on the order of those of. the amplitude: modula- ..tion broadcast band 540 to 1600 kilocycles) ,i said Lindu'ctor arm and said series capacitor being series resonant at a'irequency '(3 l-megacyclesiabove the intermediate frequencies" .(2l.9.megacycles for.

soundand 26.4 megacycles for video) of said televisionr-reeeiver and considerablyrbelow',the.television bands extending from 54 to'216 megacycles, whereby said inductor and series capacitor function as a high pass filter to reject undesired signals of frequencies below the series resonant frequency, both of said capacitors functioning as a capacitance divider to step down the impedance between the input (150 ohms) and output (70 ohms at geometric mean of range) of said network, the parallel resonant circuit comprising both of said arms and said series capacitor being tuned to parallel resonance at a frequency (47 megacycles) close to that of the lowest television channel, whereby the output of the network appears to be capacitively reactive throughout the television band and substantial carrier frequency current flows in said output capacitor arm (23).

The invention also provides, in combination with said impedance-transformation network: a low impedance input, high impedance output, L- type selector network for coupling said 1r-type reactive network to said amplifier stage, comprising: an output shunt capacitor arm 29 and series manually variable inductance i3, 23, connected between the high potential terminal 24 of the output arm of said 1rtype reactive network and the last-mentioned output arm (29), said L-type network being tuned to series resonance to select the desired television channel and at the same time providing impedance transformation irom a low impedance at its input to the high impedance at its output, thus adequately matching the input impedance of said amplifier stage.

v5 The invention also provideszmeanszior stabilizing the input capacitance and conductance of zsa'idctube comprising ar-stahilizingrresistor 1:32) "inilbiiflllltiiwillh-illhe .cathdde iof i-tube .eI'O) and -capacitance :between :the :zcathode and :control l0 -electro de:.-(of: tube: I 0) l. comprising a ZSBIElES :com-

cbination: of :saidr-output:iarm'rcapacitor ;('2 9) ;.and -anot1-1er: apafcitor M633). This :other capacitor 33) ajszsinisshunt vritli;tl1e.:cathode resistor i (32) 2andrzhaszrreactancezlargewwitlr'respect; to said: re-

:sistor. 132) -'i'Ihescutputi arimcapacitor1 l29)::;has

a;'reac.ta nce :largewwith:respectcto' said: otherv ca- ;pacitor. (33) .liAnzzinductive. plate .load is included \;'in.,the cutputzcircuitioft. the; radio frequency: am- :p'lifiersitube (I0).

:Eurther; ina accordance: witlrthe invention, both -input :and v:uutput 5 selector ":networks smaintain their Widespassx bands throughout? the 'range :of '1 operation, both.-;the:-'R; 'F. aampiifien stage andilthe -niixer 3 stage i shaving plate loads which .appear 2firrinductivezto' their input acircuits, thus .tintroducing z negativerresistancei factorstwhich: effectively :increaseithe iilfsiofthe selectivetinputicircuits.

-Accordingntozzanotherg featurexofsthe. invention. stray: inductance is: minimized :byxproviding: in-

rtegrhlztangs :lsuch: as 1 88,: Fig:36) projecting at rightzangles'ifromz;thei metazllic :support 1(91) aand azsolderi-ng zithose r tangs.:.directly .to their .correspondingc socket-terminals :(such \as 11 1-39, Fig. 2) the ssofcket terminalrhaving;:.:been:.bents approximatcly intocparallelismiwith the chassisf for that :purpose.

snnotheradvantage is provi'dedin that .thecath- -ode resistor iunctions notonlyias a st'a-bili'zing resistor: but also: asratacathode'abias resistor.

A0 1 Qtherzaduantages of ithe'iapresent invention re- "side in:theses'twotfacts: '(1)"- This tuner is con- ;tinuouslyaztunablei throughout-the range from 54= imegacyclesitcfi2t6zmegacycles ;I (-2 'Ihe pass-band of this tuner is maintained sufiiciently wide to 5 pass the signal components of any of the selected television channels, throughout this very broad range of operation. In order to preserve adequate uniformity of pass band in the radio frequency and mixer stages, it is necessary to provide means for effectively increasing the Qs of the grid input circuits of tubes Ill and II as the operating frequency is increased. Each of the plate loads in these two stages appears inductive to the corresponding input circuit, thereby pro- 55 viding regeneration which increases the Q of the grid input. This regenerative effect becomes more pronounced with frequency increase because 7 of the coaction of two factors: (1) The capacitive reactance between grid and plate decreases 5 with increasing frequency; (2) The inductive reactance of the plate leads increases with increasing frequency.

While there has been shown and described what is at present considered to be the preferred embodiment of the invention, it will be obvious to those skilled in the art that various modifications and substitutions of equivalents may be made therein without departing from the true spirit of the invention and the scope of the claims appended hereto. While the illustrative embodiment shown is used in conjunction with an unbalanced input system, it can easily be used with a balanced input system by a simple expedient which will be well known to those skilled in the art, and that is by providing a tap on inductor 15 2| and connecting that tap to terminal 25, omitting the connection between terminals 2'! and 25; such expedients as that being per se so well .known in the art that there is no necessity to ilarms, said network comprising an input shunt inductor arm connected across said transmission line, a series capacitor connected between the arms and an output shunt capacitor arm, said inductor arm providing attenuation against carrier signals having frequencies on the order of those of the amplitude modulation broadcast band (540 to 1600 kilocycles), said inductor arm and said series capacitor being series resonant at a frequency above the intermediate frequencies of said television receiver and considerably below the television bands extending from 54 to 216 megacycles, whereby said inductor and series capacitor function as a high pass filter to reject the undesired signals of frequencies below the series resonant frequency, both of said capacitors functioning as a capacitance divider to step down the impedance between the input and output of said impedance-matching network, the circuit comprising both of said arms and said series capacitor being tuned to parallel resonance at a frequency close to that of the lowest television channel, whereby the output of the impedance-matching network appears to be capacitively reactive throughout the television band and substantial carrier frequency current is built up across said output capacitor arm; Second, a low impedance input, high impedance output, L-type selector network, comprising: an output shunt capacitor arm and series manually variable inductance, connected between the high potential terminal of the output arm of said 1r-type reactive impedance-matching network and the selector network output arm, said L-type network being tuned to series resonance to select the desired television channel and at the same time providing impedance transformation from a low impedance at its input to a high impedance at its output; and, Third, a radio frequency amplifier stage having a cathode-control electrode input circuit coupled to the output shunt capacitor arm of said selector network, and means for stabilizing the input capacitance and conductance of said tube comprising a stabilizing resistor in circuit with said cathode and the capacitance between said cathode and control electrode which consists of a series combination of said output arm capacitor of said selector network and another capacitor connected in shunt with said stabilizing resistor.

2. In an input tuner for a television receiver. the combination in accordance with claim 1 and an anode load including a tuned selector network in the output circuit of said radio frequency amplifier stage, said load appearing inductive to the input circuit of said stage and cooperating with the interelectrode capacitance of the amplifier tube to introduce regeneration.

EMMERY J. H. BUSSARD.

References Cited in the file of this patent UNITED STATES PATENTS Number Name Date 2,144,009 Barber Jan. 17, 1939 2,263,613 Conron Nov. 25, 1941 2,264,890 Root Dec. 2, 1941 2,268,672 Plebanski Jan. 6, 1942 2,422,381 White June 1'7, 194? 2,474,769 Young Jun 28, 1949 FOREIGN PATENTS Number Country Date 109,863 Australia Feb. 29, 1940 

